The impedance transformation property of passive mixers enables integrated high-Q channel selection at RF with a programmable center frequency through a clock [1,2]. As such, this technique is suitable for addressing both linearity and flexibility requirements in wideband and cognitive radio applications. However, given the typically low resistance level at the RF side of the receiver chain, the RC product necessary for filtering results in large capacitors, and, consequently, large die area that does not scale with technology. In addition, filter rejection at the RF side is limited by the resistance of the switches of the passive mixer. Thus, large switches are typically needed for moderate rejection values (5Ω switches for 16dB rejection [2]), which translates to higher power consumption in the LO buffers. Furthermore, filtering prior to the LNA [1] or eliminating it altogether [3] improves linearity at the expense of noise and switching harmonics being injected directly at the antenna node. Conversely, an LNA first architecture offers an opposite trade-off. This work demonstrates a highly compact design of a direct conversion receiver with an active feedback frequency translation loop to perform channel selection at the LNA output while simultaneously cancelling its distortion. Figure 9.3.1 (top) shows the proposed architecture. Signals at the antenna are down-converted and amplified. Along the feedback path, the desired signal BW, now centered at DC, is rejected using a HPF, while interferers are up-converted and fed back at the LNA output. With a high loop gain, node 'A' becomes a virtual ground for interferers beyond the corner frequency of the HPF, which effectively creates a channel select filter at node 'A'. Since the feedback loop sinks current, filter rejection at the RF side is not limited by the resistance of the down-conversion mixer switches. As opposed to other feedback-based receivers [4,5], the proposed architecture incorporates the receiver's downconversion path within the loop to provide an IF output instead of having a separate rejection loop after the LNA with an RF output that needs further down-conversion.The channel bandwidth is now determined by the corner frequency of the HPF (ωHPF) divided by 1+TO, where TO is the loop gain ( Fig. 9.3.1-bottom). That is, for a given bandwidth, the capacitance needed for channel selection, and therefore die area, is reduced by the available loop gain. The loop bandwidth (ωDOM) sets an upper limit on the frequency range of interferers that can be suppressed. Such a filtering loop is therefore suitable for implementation in a modern high speed process and its performance is expected to improve with technology scaling.To cancel LNA distortion, the V-to-I conversion circuits of the LNA and feedback amplifier are matched (Fig. 9.3.2). Under this condition, a downconverted inverted replica of input interferers is forced at the output via the feedback action, causing the feedback amplifier to perfectly sink the distortion currents sourced by the LNA. This arr...